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preliminary product information this document contains information for a new product. cirrus logic reserves the right to modify this product without notice. 1 copyright . cirrus logic, inc. 2000 (all rights reserved) p.o. box 17847, austin, texas 78760 (512) 445 7222 fax: (512) 445 7581 http://www.cirrus.com cs61581 t1/e1 universal line interface features provides t1 and e1, long haul and short haul line interface provides a qrss test signal and error detector impedance matching line driver using a single transformer greater than 14 db of transmit return loss without using external resistors no crystal needed for jitter attenuation meets at&t 62411 and tbr 12/13 jitter tolerance and attenuation requirements meets ansi t1.231b and itu-t g.775 requirements for los and ais meets the bs6450 transmitter short-circuit requirements for e1 applications compliant with: C itu-t recommendations: g.703, g.732, g.775 and i.431 C american national standards (ansi): t1.102, t1.105, t1.403, t1.408, and t1.231 C fcc rules and regulations: part 68 and part 15 C at&t publication 62411 C etsi ets 300 011, 300 233, tbr 12/13 C tr-net-00499 description the cs61581 is a primary rate line interface unit capa- ble of operation in both short haul (intraoffice) and long haul applications. the cs61581 combines the com- plete analog transmit and receive circuitry for a single, full-duplex interface at t1 and e1 rates. the device is pin and function compatible with the level one lxt310 and lxt318 (the latter in the host mode only). the de- vice can also replace lxt359 and lxt360. enhanced functionality is available through an extended register set allowing short haul operation, custom pulse shape generation, qrss pattern generation, detection and er- ror counting, and generation and detection of loop up and loop down codes. the cs61581 features crystal ? low-power impedance-matched line drivers and crystal- less jitter attenuation. ordering information CS61581-IL 28-pin plcc cs61581-ip 28-pin pdip ds211pp8 apr 00 tclk tdata/tpos ubs/tneg jasel rclk rdata/rpos bpv/rneg int/nloop los 2 3 4 e n c o d e r 11 q r s s remote loopback 8 7 6 d e c o d e r 23 12 inband nloop & los processor receive clock generator 9 10 xtalin xtalout 521221415 mode rv+ rgnd tgnd tv+ jitter atten timing & data recovery los/ nloop clear registers & control logic taos enable lbo select jitter atten transmit timing & control pulse shaping circuitry rom / ram line drivers serial port lloop enable local loopback (analog) sh/lh equalizer control slicers & peak detect noise & crosstalk filters sh magnitude equalizer agc sh 13 16 28 26 27 24 25 18 19 20 1 ttip tring clke/taos cs/rloop sclk/lloop sdi/lbo1 sdo/lbo2 latn rtip rring mclk local loopback (digital) copyright ? cirrus logic, inc. 2005 (all rights reserved) http://www.cirrus.com cs61581 t1/e1 universal line interface aug ?05 ds211f1
c s 6 1 5 8 1 2 d s 2 1 1 p p 8 t a b l e of c ont e nt s 1 . c h a r a c t e r i s t i c s a n d s p e c i f i c a t i o n s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 a b s o l u t e m a x i m u m r a t i n g s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 r e c o m m e n d e d o p e r a t i n g c o n d i t i o n s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 d i g i t a l c h a r a c t e r i s t i c s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4 a n a l o g s p e c i f i c a t i o n s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5 t 1 s w i t c h i n g c h a r a c t e r i s t i c s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 e 1 s w i t c h i n g c h a r a c t e r i s t i c s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 s w i t c h i n g c h a r a c t e r i s t i c s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 9 2 . t h e o r y o f o p e r a t i o n . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 0 2 . 1 o p e r a t i n g m o d e s e l e c t i o n . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 0 2 . 2 m a s t e r c l o c k s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 0 2 . 3 t r a n s m i t t e r . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 0 2 . 4 t r a n s m i t a l l o n e s s e l e c t . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 2 2 . 4 . 1 r e c e i v e r . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3 2 . 4 . 2 s h o r t h a u l . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3 2 . 4 . 3 l o n g h a u l . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3 2 . 4 . 4 c l o c k r e c o v e r y . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 3 2 . 4 . 5 j i t t e r t o l e r a n c e . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 4 2 . 5 r e c e i v e r l i n e a t t e n u a t i o n i n d i c a t i o n . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 4 2 . 6 j i t t e r a t t e n u a t o r . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 4 2 . 7 r e c e i v e r l o s s o f s i g n a l . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 4 2 . 8 l o c a l l o o p b a c k . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 5 2 . 9 r e m o t e l o o p b a c k . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 6 2 . 1 0 n e t w o r k l o o p b a c k . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 6 2 . 1 1 a l a r m i n d i c a t i o n s i g n a l . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 6 2 . 1 2 s e r i a l i n t e r f a c e . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 6 2 . 2 1 i n t e r r u p t s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 3 3 . q r s s t e s t m o d e . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 3 4 . a r b i t r a r y w a v e f o r m g e n e r a t i o n . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 4 4 . 1 p o w e r o n r e s e t / r e s e t . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 5 4 . 2 p o w e r s u p p l y . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 6 6 . p i n d e s c r i p t i o n . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 1 6 . 1 p o w e r s u p p l i e s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 2 6 . 2 o s c i l l a t o r . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 2 6 . 3 c o n t r o l . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 2 6 . 4 s t a t u s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 3 6 . 5 s e r i a l c o n t r o l i n t e r f a c e . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 3 6 . 6 d a t a i n p u t / o u t p u t . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 4 7 . p a c k a g e d i m e n s i o n s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 3 6 cs61581 2 ds211f1
cs61581 ds211pp8 3 list of figures figure 1. signal rise and fall characteristics ............................................................................... 8 figure 2. recovered clock and data switching characteristics.................................................... 8 figure 3. transmit clock and data switching characteristics ....................................................... 8 figure 4. serial port write timing diagram ................................................................................... 9 figure 5. serial port read timing diagram ................................................................................... 9 figure 6. typical pulse shape at dsx-1 cross connect............................................................. 12 figure 7. mask of the pulse at the 2048 kbps interface............................................................... 12 figure 8. minimum input jitter tolerance of receiver ................................................................. 13 figure 9. latn pulse width encoding ......................................................................................... 14 figure 10.typical jitter transfer function - t1 ............................................................................. 15 figure 11.typical jitter transfer function - e1 ............................................................................. 15 figure 12.input/output timing (showing address 0x10) ............................................................... 17 figure 13.phase definition of arbitrary waveforms ...................................................................... 24 figure 14.example of summing of waveforms............................................................................. 25 figure 15.matched impedance output configuration ................................................................... 28 figure 16.low impedance output configuration .......................................................................... 29 figure 17.typical system connection .......................................................................................... 30 list of tables table 1. pulse shape selection and transformer requirements ................................................. 11 table 2. data output/clock relationship ...................................................................................... 13 table 3. register map.......................................................................................................... ......... 17 table 4. register 0x10 decoding................................................................................................ .. 23 table 5. register 0x10 decoding................................................................................................ .. 23 table 5. diagnostic mode availability .......................................................................................... .26 table 6. transformer specification ............................................................................................. .. 26 table 7. recommended transformers for the cs61581 .............................................................. 27 cs61581 ds211f1 3
cs61581 4 ds211pp8 1. characteristics and specifications absolute maximum ratings warning: operations at or beyond these limits may result in permanent damage to the device. normal operation is not guaranteed at these extremes notes: 1 transient currents of up to 100 ma will not cause scr latch-up. also ttip, tring, tv+ and tgnd can withstand a continuous current of 100 ma. recommended operating conditions notes: 1. tv+ must not exceed rv+ by more than 0.3 v. 2. power consumption while driving line load over operating temperature range. includes ic and load. digital input levels are within 10% of the supply rails and digital outputs are driving a 50 pf capacitive load. 3. typical consumption corresponds to 50% ones density and medium line length at 5.0 v. 4. maximum consumption corresponds to 100% ones density and maximum line length at 5.25 v. digital characteristics (ta = -40 c to 85 c; tv+, rv+ = 5.0 v 5%; gnd = 0 v) notes: 5. this specification guarantees ttl compatibility (v oh = 2.4 v @ i out = -40 a). 6. output drivers are ttl compatible and will drive cmos logic levels into a cmos load. parameter symbol min max units dc supply (referenced to rgnd=tgnd=0 v) rv+ tv+ - - 6.0 (rv+) + 0.3 v v input voltage, any pin v in rgnd-0.3 (rv+) + 0.3 v input current, any pin (note 1) i in -10 10 ma ambient operating temperature t a -40 85 c storage temperature t stg -65 150 c parameter symbol min typ max units dc supply (note 1) rv+, tv+ 4.75 5.0 5.25 v ambient operating temperature t a -40 25 85 c power consumption, long haul (notes 2,3,4) low z match z p c - - 390 400 630 575 mw power consumption, short haul (notes 2,3,4) low z match z p c - - 480 430 725 650 mw parameter symbol min typ max units high-level input voltage (note 5) pins 1-4, 24-28 v ih 2.0 - - v low-level input voltage (note 5) pins 1-4, 24-28 v il --0.8v high-level output voltage (notes 5, 6) i out = -40 a pins 6-8, 25 v oh 2.4 - - v low-level output voltage (notes 5, 6) i out = 1.6 ma pins 6-8, 25 v ol --0.4v input leakage current - - 10 a cs61581 4 ds211f1
cs61581 ds211pp8 5 analog specifications (ta = -40 c to 85 c; tv+, rv+ = 5.0 v 5%; gnd = 0 v) notes: 7. using a 0.47 f capacitor in series with the primary of a transformer recommended in the applications section. 8. pulse amplitude measured at the output of the transformer across a 75 . load for line length settings len[2:0] = 001 and 000. 9. pulse amplitude measured at the output of the transformer across a 120 . load for line length setting len[2:0] = 000. 10. pulse amplitude measured at the output of the transformer across a 100 . load for line length setting len[2:0] = 000. 11. pulse amplitude measured at the dsx-1 cross-connect for all line length settings from len[2:0] = 011 to len[2:0] = 111. 12. assuming that jitter free clock is input to tclk. jitter attenuator not in path. 13. not production tested. parameters guaranteed by design and characterization. 14. measured broadband through a 0.5 . resistor across the secondary of the transmitter transformer during the transmission of an all ones data pattern with len[2:0] = 000 or 001. parameter min typ max units transmitter ami output pulse amplitudes (note 7) e1, 75 . (note 8) e1, 120 . (note 9) t1, (fcc part 68) (note 10) t1, dsx-1 (note 11) 2.14 2.7 2.7 2.4 2.37 3.0 3.0 3.0 2.6 3.3 3.3 3.6 v v v v external equalizer pulse amplitude 4.8 5.6 6.4 v transmitter output impedance (note 13) transformer turns ratio = 1:2 low z, long haul 1.5 . transformer turns ratio = 1:1.5 e1, 75 . e1, 120 . t1, fcc t1, dsx1 t1, ext. equal 33 53 44 44 44 . . . . . jitter added by the transmitter (note 12, 13) 10 hz - 8 khz 8k hz - 40 khz 10 hz - 40 khz broad band - - - - 0.015 0.015 0.015 0.020 - - - - ui ui ui ui power in 2 khz band about 772 khz (notes 7, 18) 12.6 15 17.9 dbm power in 2 khz band about 1.544 mhz (notes 7, 18) (referenced to power in 2 khz band at 772 khz) -29 -38 - db positive to negative pulse imbalance (notes 7, 13) - 0.2 0.5 db transmitter short circuit current (notes 7, 14) - - 50 ma rms
cs61581 6 ds211pp8 ana l o g spec i f i ca t i o ns ( continued ) notes: 15. data decision threshold established after the receiver equalizer filters pulse overshoot and undershoot. 16. jitter tolerance for 0 db input signal level. jitter tolerance increases at lower frequencies. see figure 8. 17. see receiver jitter tolerance plot, figure 8. 18. guaranteed by design. parameter min typ max units receiver rtip/rring input impedance - 20k - . sensitivity below dsx (0 db = 3.0 v) long haul, t1 -40 30 - - - - db mv sensitivity below dsx (0 db = 3.0 v) long haul, e1 -36 48 - - - - db mv sensitivity below dsx (0 db = 3.0 v) t1 - short haul -21 270 - - - - db mv sensitivity below g.703 (0 db = 2.4 v) e1 - short haul -15 430 - - - - db mv loss of signal threshold (note 18) long haul, t1 & e1 t1 short haul e1 short haul - - - -42 -22 -16 - - - db db db data decision threshold (note 18) (note 15) t1, dsx-1 t1, (fcc part 68) and e1 - - 50 50 - - % of peak % of peak allowable consecutive zeros before los 160 175 190 bits receiver input jitter tolerance - short haul (note 16) e1: 18 khz - 100 khz t1: 10 khz - 100 khz (note 13) 2 khz (note 18) 10 hz and below 0.20 0.4 6.0 300 - - - - - - - - ui ui ui ui receiver input jitter tolerance - long haul (note 17) e1:10 khz - 100 khz t1:10 khz - 100 khz (note 13) 1 hz 0.20 0.4 138 - - - - ui ui ui cs61581 6 ds211f1
cs61581 ds211pp8 7 t1 switching characteristics (ta = -40 c to 85 c; tv+, rv+ = 5.0 v 5%; gnd = 0 v; inputs: logic 0 = 0 v, logic 1 = rv+; see figures 1, 2, & 3) notes: 19. mclk provided by an external source or tclk. 20. rclk duty cycle will be 62.5% or 37.5% when jitter attenuator fifo limits are reached. 21. at max load of 1.6 ma and 50 pf. 22. host mode (clke = 1). 23. host mode (clke = 0) e1 switching characteristics (ta = -40 c to 85 c; tv+, rv+ = 5.0 v 5%; gnd = 0 v; inputs: logic 0 = 0 v, logic 1 = rv+; see figures 1, 2, & 3) parameter symbol min typ max units tclk frequency f tclk -1.544-mhz mclk frequency (note 19) f mclk -1.544-mhz rclk duty cycle (notes 18, 20) t pwh1 /t pw1 50 % rise time, all digital outputs (note 21) t r --85ns fall time, all digital outputs (note 21) t f --85ns tpos/tneg to tclk falling setup time t su2 25 - - ns tclk falling to tpos/tneg hold time t h2 25 - - ns rpos/rneg valid before rclk falling (note 22) t su1 150 274 - ns rpos/rneg valid before rclk rising (note 23) t su1 150 274 - ns rpos/rneg valid after rclk falling (note 22) t h1 150 274 - ns rpos/rneg valid after rclk rising (note 23) t h1 150 274 - ns parameter symbol min typ max units tclk frequency f tclk -2.048-mhz mclk frequency (note 19) f mclk -2.048-mhz rclk duty cycle (notes 18, 20) t pwh1 /t pw1 50 % rise time, all digital outputs (note 21) t r --85ns fall time, all digital outputs (note 21) t f --85ns tpos/tneg to tclk falling setup time t su2 25 - - ns tclk falling to tpos/tneg hold time t h2 25 - - ns rpos/rneg valid before rclk falling (note 22) t su1 100 194 - ns rpos/rneg valid before rclk rising (note 23) t su1 100 194 - ns rpos/rneg valid after rclk falling (note 22) t h1 100 194 - ns rpos/rneg valid after rclk rising (note 23) t h1 100 194 - ns cs61581 ds211f1 7
cs61581 8 ds211pp8 any digital output t r t f 10% 10% 90% 90% figure 1. signal rise and fall characteristics rclk t pw1 t pwl1 t pwh1 (clke = 1) (clke = 0) rclk rpos rneg su1 h1 tt figure 2. recovered clock and data switching characteristics tclk tpos/tneg t su2 t h2 t pwh2 t pw2 figure 3. transmit clock and data switching characteristics cs61581 8 ds211f1
cs61581 ds211pp8 9 switching characteristics (ta = -40 to 85 c; tv+, rv+ = 5v 5%; inputs: logic 0 = 0 v, logic 1 = rv+) notes: 24. output load capacitance = 50 pf parameter symbol min typ max units sdi to sclk setup time t dc 50 - - ns sclk to sdi hold time t cdh 50 - - ns sclk low time t cl 240 - - ns sclk high time t ch 240 - - ns sclk rise and fall time t r , t f - - 50 ns cs to sclk setup time t cc 50 - - ns sclk to cs hold time t cch 50 - - ns cs inactive time t cwh 250 - - ns sclk to sdo valid (note 24) t cdv --200ns cs to sdo high z t cdz -100-ns t dc t cc lsb lsb msb control byte data byte cs sclk sdi t ch t cwh t cch t cdh t cl t cdh figure 4. serial port write timing diagram high z cs sclk sdo clke = 1 sdi cdv t cdv t cdz t sdo clke = 0 last addr bit d0 d1 d6 d7 d0 d1 d6 d7 figure 5. serial port read timing diagram cs61581 ds211f1 9
cs61581 10 ds211pp8 2. theory of operation the cs61581 universal line interface supports t1 and e1 data rates for both short haul and long haul applications. the transmitter complies with all standard t1 and e1 applications without changing transformers. transmitter power consumption is minimized using the impedance matching feature, which eliminates external resistors for standard line impedances. when configured for long haul opera- tion, the receiver uses gain and equalization to pro- vide 40 db of sensitivity. the receiver reconfigures for short haul operation, limiting the receive sensi- tivity and increasing the noise immunity. 2.1 operating mode selection the cs61581 can be operated in stand-alone hard- ware interface mode (mode pin is low), or by a microcontroller in serial host mode (mode pin is high). additional functionality is available in the host mode including both short haul and long haul operational modes. the cs61581 defaults to the long haul configuration (lxt310/318 compati- ble). the t1 (dsx-1 and network interface) and e1 (itu-t g.703) are selectable via the serial port by writing to a control register. tying tneg high for more than 16 tclk cycles enables the unipolar mode, changing tpos to tdata, rpos to rdata, and rneg to bpv. when configured for unipolar mode, the mode pin can be tied to rclk enabling the b8zs encod- ers and decoders. coder mode does not support bi- polar data. 2.2 master clocks the cs61581 requires a reference clock for the re- ceiver and the jitter attenuator. either a 1.544 mhz (or 2.048 mhz) external clock can be input to mclk, or a 4x crystal can be connected to the on- chip oscillator. this frequency reference should be within 100 ppm of the nominal operating frequen- cy. jitter and wander on the reference clock will de- grade jitter attenuation and receiver jitter tolerance. if mclk is provided, the crystal oscillator is ig- nored. 2.3 transmitter the transmitter accepts digital t1 or e1 input data and drives appropriately shaped ami (alternate mark inversion) pulses onto a transmission line through a transformer. the transmit data (tpos & tneg or tdata) is sampled on the falling edge of the input clock, tclk. upon power up, the cs61581 defaults to long haul mode with low-impedance drive. in this mode, a 1:2 transformer is required (see table 1). the cs61581 will support both t1 and e1 opera- tion as determined by the master clock frequency. in host mode, t1 (dsx-1 or network interface), e1 (itu-t or g.703) or t1 long-haul pulse shapes may be selected. long-haul or short-haul operation is determined by the sh/lh bit (cr2.0). the sh/lh bit also establishes functionality of control registers 1 and 2. in the matched impedance configuration, the line driver internally matches the impedance of the line load; 75 . or 120 . for e1, and 100 . for t1 using a 1:1.5 turns ratio transformer. internal impedance matching reduces current consumption by about a factor of two compared to return loss achieved by external resistors. the t1 long-haul pulse shapes comply with fcc part 68 option a (0 db). option b (-7.5 db), op- tion c (-15 db) or (-22.5 db) (see table 1). if de- sired, the t1 pre-equalization settings can be selected for e1 operation as well. in long-haul mode, pulse shaping and signal level are controlled by lbo1 and lbo2 pins or register bits. custom transmit pulse shapes may be implemented by writing pulse shape coefficients to the registers. custom pulses may be used to correct for pulse shape degradation or distortion caused by improper termination, suboptimal interconnect wiring, or cs61581 10 ds211f1
cs61581 ds211pp8 11 loading from external components such as high voltage protection devices. for t1 dsx-1 applications, line lengths from 0 to 655 feet (as measured from the transmitter to the dsx-1 cross connect) may be selected. the five partition arrangement in table 1 meets ansi t1.102 pulse shape requirements when using #22 abam or at&t 600 series cable. a typical output pulse is shown in figure 6. these pulse settings can also be used to meet itu-t pulse shape require- ments for 1.544 mhz operation. short haul pulse shapes for t1 and e1 are selected by the len[2:0] bits in control register 1. note that when the device is operated at e1 fre- quency in the hardware mode, it defaults to low im- pedance, long haul mode. the pulses driven by the transmitter in this mode are t1.403 (350ns) pulses with an overshoot and an undershoot. to drive pulses without overshoot and undershoot in e1 long haul mode, the e1_lh bit (cr3.6) must be set to 1, with the sh/lh bit (cr2.0) set to 0. the e1 g.703 pulse shape is supported with line length selections len[2:0] = 000 for 2.37 v 75 . applications or len[2:0] = 001 for 3.0 v 120 . ap- plications. the output pulse will meet the g.703 pulse shape template shown in figure 7. the output impedance of the driver will adjust according to the pulse shape selected. in the short haul mode, setting the len[2:0] bits also controls the transmitter output impedance. for long haul operation, driver impedance is deter- mined by the desired selection of matchz and e1_lh bits. when matchz is set to ?0? the out- put impedance is low, and the impedance presented to the line is controlled by external resistors. when matchz is set to 1, e1_lh determines whether * matchz = cr2.5 long haul lb02 lb01 output pulse 0 0 0 db 0 1 -7.5 db 1 0 -15 db 1 1 -22.5 db transformer turns ratio mode transmit receive hdw or matchz* = 0 1:2 1:1 matchz* = 1 1:1.5 1:1 short haul len2 len1 len0 output pulse line z 0 0 0 e1 2.37 v 75 . 0 0 1 e1 3.0 v 120 . 011 dsx-1 0 -133 100 . 100 dsx-1 133 -266 100 . 101 dsx-1 266 -399 100 . 110 dsx-1 399 -533 100 . 111 dsx-1 533 -655 100 . 0 1 1 ansi t1.403 100 . 010fcc part 68, option a 6.0 v 100 . table 1. pulse shape selection and transformer requirements cs61581 ds211f1 11
cs61581 12 ds211pp8 the driver is set for 100 . (e1_lh = 0) or 120 . (e1_lh = 1). the cs61581 will detect the absence of tclk, and will force ttip and tring to high impedance af- ter 175 bit periods, preventing transmission when data input is not present. in host mode, the trans- mitter can be set to high impedance by setting the txhiz bit, cr2.1, to ? 1. ? when any transmit control bit (taos, len0-2, lbo1-2, or lloop) is toggled, the transmitter outputs will require approximately 22 bit periods to stabilize. the transmitter will take longer to stabi- lize when rloop is selected because the timing circuitry must adjust to the new frequency. the cs61581 has the option to drive a 6 v peak pulse. the option is used for driving external equal- izers used in t1 dsx applications that conform to fcc part 68, option a. this configuration is se- lected by setting the len[2:0] control bits in regis- ter 0x10 to 010 in the short haul configuration. the turns ratio of the transmit transformer must be set accordingly: in matched impedance mode, the turns ratio must be 1:1.5; in low impedance mode, the transformer turns ratio = 1:2.6. 2.4 transmit all ones select the transmitter provides for all ones insertion at the frequency of tclk. if tclk is absent, then mclk is used (or the quartz crystal generated fre- quency in the absence of mclk). transmit all ones is selected when taos (pin 28 in hardware mode, cr1.7 in host mode) goes high, and causes continuous ones to be transmitted on the line (ttip and tring). when taos is active, the tpos and tneg (tdata) inputs are ignored. if remote loopback is in effect, any taos request will be ig- nored. figure 6. typical pulse shape at dsx-1 cross connect 500 1.0 0.5 0 -0.5 0 250 750 1000 time (nanoseconds) output pulse shape normalized amplitude ansi ti.102, at&t cb 119 specifications 269 ns 244 ns 194 ns 219 ns 488 ns nominal pulse 0 10 50 80 90 100 110 120 -10 -20 percent of nominal peak voltage figure 7. mask of the pulse at the 2048 kbps interface cs61581 12 ds211f1
cs61581 ds211pp8 13 2.4.1 receiver the receiver extracts data and clock from the input signal and outputs clock and synchronized data. the rtip and rring inputs are biased to an inter- mediate dc level so that the input is received as a differential signal. the incoming pulses are ampli- fied, equalized and filtered before being fed to the comparator for peak detection, slicing and data re- covery. a noise and cross-talk filter removes signal components that are coupled onto the line from oth- er cables. t1 or e1 operation is determined by the transmit pulse shape selection, len[2:0]. the clock and data recovery circuit exceeds the jit- ter tolerance specifications of publications 43802, 43801, at&t 62411, tr-tsy-000170, itu-t g.823 and etsi tbr12/13. jitter tolerance is shown in figure 8. in hardware mode, the receiver is configured for long haul operation. in host mode short haul op- eration can be selected by setting the sh/lh (cr2.0) to 1. when configured for short haul, the functions of registers 0x10 and 0x11 are redefined. 2.4.2 short haul receiver sensitivity is set to comply with itu-t i.431 requirements for e1 and t1. the comparator thresholds are dynamically established at 50% per- cent of the peak level. this is acceptable for both t1 and e1 cases as pulse undershoot and overshoot are filtered internally. 2.4.3 long haul configuring the receiver for long haul operation in- creases the receive sensitivity. to select long haul mode, the sh/lh (cr2.0) bit must be set to 0; for e1 long haul mode, the e1_lh bit (cr3.6) must be set to 1. 2.4.4 clock recovery the clock recovery circuit is a third-order phase lock loop. the clock and data recovery circuit is tolerant of long strings of consecutive zeros, and will successfully receive a 1-in-175, jitter-free in- put signal. in hardware mode, data on rpos and rneg (rdata), is stable on the rising edge of recovered clock, rclk. in host mode, clke (pin 28) deter- mines the clock polarity for which output data is valid, as shown in table 2. when clke is high, rpos and rneg (rdata) are valid on the fall- ing edge of rclk. when clke is low, rpos and rneg are valid on the rising edge of rclk. table 2. data output/clock relationship 10 1k 10k 1 100 100k 700 .1 1 10 100 .4 28 300 300 peak-to-peak jitter (unit intervals) jitter frequency (hz) performance 138 minimum at&t 62411 g. 82 3 figure 8. minimum input jitter tolerance of receiver mode (pin 5) clke (pin 28) data clock clock edge for valid data low don t care rpos rneg rclk rising high low rpos rneg sdo rclk rclk sclk rising rising falling high high rpos rneg sdo rclk rclk sclk falling falling rising cs61581 ds211f1 13
cs61581 14 ds211pp8 2.4.5 jitter tolerance the receiver jitter tolerance is shown in figure 8. the cs61581 jitter tolerance exceeds at&t 62411 in t1 applications, and g.823 in e1 applica- tions. 2.5 receiver line attenuation indication latn (pin 18) outputs a coded signal that repre- sents the signal level at the input of the receiver. as shown in figure 9, the latn output is measured against rclk to provide the signal level in 7.5 db increments. in host mode, the receive input signal level can be read from the equalizer gain register (address 0x12), to greater resolution, dividing the input range into 20 steps of 2 db increments. 2.6 jitter attenuator the jitter attenuator reduces the amount of jitter and wander in the input signal. the jitter attenuator is built around a fifo; the write pointer of the fifo is driven by the input clock, and the read pointer is driven by a phase locked loop (pll). the jitter attenuator can be placed in either the transmit or receive paths; in the transmit path, writing to the fifo is controlled by tclk; if the jitter attenuator is in the receive path, writing is controlled by the recovered clock from the input data. the jitter at- tenuator does not require an external crystal. if a crystal is present, the pll uses it for a reference; otherwise, mclk provides the reference. the jitter attenuator is enabled if an external crystal is connected. if no crystal is present, then the jitter attenuator is enabled by either grounding or float- ing xtalin (pin 9). it is disabled by tying xtalin high. it is placed in the transmit or re- ceive paths by setting jasel (pin 11) either low or high, respectively. the jitter attenuator has two modes of operation de- pending on whether the cs61581 is configured for t1 or e1 operation (based on the output pulse shape selection). for t1, the jitter attenuator corner frequency is set at 4 hz, with attenuation increas- ing at a 20 db per decade rate above 4 hz. for e1 the corner frequency is approximately 1.25 hz in order to comply with etsi 300 011, tbr12/13, and recommendation i.431 complying to these specifications also guarantees compliance to less stringent standards, such as g.736. typical jitter at- tenuation curves are shown in figures 10 and 11. 2.7 receiver loss of signal the receiver will indicate loss of signal by assert- ing los (pin 12, also cr1.0 in host mode). this happens on power up, reset, when the receiver gain reaches its maximum, or on receiving 175+/-15 consecutive zeros. received zeros are counted based on recovered clock cycles. when in the los state, received data is not output from rpos/rneg (rdata); but is squelched until the device comes out of los. the los condition is ex- rclk latn 1 2 3 4 5 latn = 1 rclk, 7.5 db of attenuation latn = 2 rclk, 15 db of attenuation latn = 3 rclk, 22.5 db of attenuation latn = 4 rclk, 0 db of attenuation figure 9. latn pulse width encoding cs61581 14 ds211f1
cs61581 ds211pp8 15 ited using the ansi t1.231-1993 and itu-t g.775 criteria, namely 12.5% ones density for 175+/-75 bit periods with no more than 100 consecutive ze- ros. in long haul operation, the receiver recovers signals down to -40 db for t1 and -36 db for e1. in short haul mode, the receive sensitivity is typically - 21 db for t1 and -15 db for e1, in accordance with i.431 and g.775. los will be declared beyond these signal levels. these los thresholds are com- pliant with all short haul applications. in los, the rclk frequency depends on whether mclk is applied, and whether the jitter attenuator is in the transmit or receive path. if the jitter atten- uator is in the receive path, the jitter attenuator will hold over the average incoming data frequency pri- or to los. rpos (rdata) and rneg pins are forced low upon los. when the jitter attenuator is in the transmit path or not used, the clock recovery is referenced to mclk, if provided, or the crystal oscillator. the frequency of rclk in this case will simply remain slaved to the clock reference upon loss of data. the recovered clock remains as a 50% duty cycle clock. the digital pll in the clock recovery circuit of the cs61581 generates an internal data clock from the edges of the incoming pulses (1 ? s). timing is recovered by a phase selector which se- lects one of the phases from the internal synchroni- zation clock (one of three clocks, 120 degrees apart in phase, at 16x the data rate). since the selection is made between a limited set of phases, the digital timing recovery process has a small phase error built into the sampling process. by choosing 48 possible sampling phases, the cs61581 reduces the sampling error to a minimum. 2.8 local loopback local loopback is selected by setting lloop high (pin 27 in hardware mode, cr1.6 in host mode). selecting local loopback causes the clock and data on tclk, tpos and tneg (tdata) to be output on rclk, rpos and rneg (rdata). the rtip/rring inputs have no effect on rclk, rpos and rneg (rdata) in this mode. inputs to the transmitter are still transmitted on ttip and tring unless taos has been selected, in which case ami-encoded continuous ones are transmitted at the tclk frequency. attenuation in db frequency in hz 10 20 30 40 50 60 1101001k10k maximum attenuation limit 62411 requirements minimum attenuation limit measured performance 0 figure 10. typical jitter transfer function - t1 attenuation in db frequency in hz 10 20 30 40 50 60 1 20 2400 18 k 100 k 0 g.736 tbr12/13 measured performance minimum attenuation limits figure 11. typical jitter transfer function - e1 cs61581 ds211f1 15
cs61581 16 ds211pp8 2.9 remote loopback remote loopback is selected by setting rloop high (pin 26 in hardware mode, cr1.5 in host mode). in remote loopback, the recovered clock and data input on rtip and rring are sent back out on the line via ttip and tring. selecting re- mote loopback overrides a taos request. the re- covered clock and data from the incoming signal are also sent to rclk, rpos and rneg (rdata). si- multaneous selection of local and remote loopback modes will cause a device reset to occur (see reset). 2.10 network loopback during network loopback (automatic remote loopback), the data path and operation of the device is identical to remote loopback, except this loop- back mode is controlled by the transmitter at the other end of the loop. it is initiated by enabling net- work loopback detection on the device. in host mode, network loopback (nloop) detection is enabled by writing ones to taos, lloop and rloop, then clearing them. in hardware mode, network loopback can be enabled by tying rloop to rclk or by setting taos, lloop, and rloop high for at least 200 ns, and then low. once enabled network loopback functionality will remain in effect until rloop is activated or the device is reset. when nloop detection is enabled, the receiver monitors the input data stream for the loop up data pattern: a repeating 00001. when this pattern is repeated for a minimum of five seconds (with less than 10 -3 ber), the device sets its internal data path as in remote loopback. it stays in this mode until the loop down pattern (repeating 001) is received for 5 seconds, or by activation of rloop. nloop is temporarily suspended by lloop, but the nloop state is not reset. the device can also generate the loop up and loop down sequences by setting the loopup (cr2.3) or loopdn (cr2.4) bits respectively. the network loopback generation and detection functions are only available in long haul mode. 2.11 alarm indication signal the receiver sets the register bit, ais, to ? 1 ? when less than 9 zeros are detected out of 8192 bit peri- ods. ais returns to ? 0 ? upon the first read after the ais condition is removed, determined by 9 or more zeros out of 8192 bit periods. some operations change the definition of other bits. writing a 1 or 0 to sh/lh (cr2.0 = 1), places the device in short haul or long haul mode respec- tively, and the definition of control registers 1 and 2 are modified accordingly. in long haul mode, e1 operation can be enabled by setting e1_lh to 1 (cr3.6 = 1), changes cr 1.2 from b8zs to hdb3. enabling unipolar mode by setting tneg (pin 4) high for 16 clocks allows the user to enable coder mode us- ing the coder bit (cr1.2lh). when tneg is low, enabling bipolar mode, cr1.2lh is the taz bit (transmit all zeroes). 2.12 serial interface in the host mode, pins 24 through 28 serve as a mi- crocontroller interface. on-chip registers can be written to via the sdi pin or read from via the sdo pin at the clock rate determined by sclk. through these registers, a host controller can be used to con- trol operational characteristics and monitor device status. the serial port read/write timing is indepen- dent of the system transmit and receive timing. data transfers are initiated by taking the chip select input, cs , low (cs must initially be high). address and input data bits are clocked in on the rising edge of sclk. the clock edge on which output data is stable and valid is determined by clke as shown in table 2. data transfers are terminated by setting cs high. cs may go high no sooner than 50 ns after the rising edge of the sclk cycle corresponding to the last write bit. for a serial data read, cs may go high any time to terminate the output and set sdo to high impedance. cs61581 16 ds211f1
cs61581 ds211pp8 17 figure 12 shows the timing relationships for data transfers when clke = 0. when clke = 1, data bit d7 is held until the falling edge of the 16th clock cycle. when clke = 0, data bit d7 is held valid until the rising edge of the 17th clock cycle. sdo goes high-impedance after cs goes high or at the end of the hold period of data bit d7. sdo goes to a high impedance state when not in use. sdo and sdi may be tied together in applica- tions where the host processor has a bidirectional i/o port. an address/command byte, shown in figure 12, points to addresses 0x10 through 0x15 (address 0x10 shown), and precedes a data byte. the first bit of the address/command byte determines whether a read or a write is requested. the next six bits con- tain the address. the last bit is ignored. data to the internal registers is input on the eight clock cycles immediately following the address/command byte. the register bit assignments are shown in table 3. cs sclk sdo clke = 0 sdi d6 d5 d4 d3 d2 d1 d0 d7 0 0 d7 d6 d5 d4 d3 d2 d1 d0 address/command byte data input/output 0 0 0 1 0 r/w figure 12. input/output timing (showing address 0x10) 76543210addr control register 1 lh (cr2.0 = 0) (cr1lh) taos lloop rloop lb02 lb01 coder taz nloop los 0x10 r/w control register 1 sh (cr2.0 = 1) (cr1sh) taos lloop rloop len2 len1 len0 rsvd los 0x10 r/w control register 2 lh (cr2.0 = 0) (cr2lh) ais ramplse matchz loopdn loopup rpwdn txhiz sh/lh 0x11 r/w control register 2 sh (cr2.0 = 1) (cr2sh) ais ramplse matchz rsvd rcoder tcoder txhiz sh/lh 0x11 r/w equalizer gain (eqgain) x x x eq4 eq3 eq2 eq1 eq0 0x12 r ram address (ram) msb - - - - - - lsb 0x13 r/w control register 3 (cr3) qrss- path e1_lh rst_ qerr qdet ins_qerr qsync test qgen test 0x14 r/w data pattern error count (dpec) msb - - - - - - lsb 0x15 r table 3. register map cs61581 ds211f1 17
cs61581 18 ds211pp8 2.13 control register 1 lh (cr2.0 = 0): address 0x10 taos transmit all ones select when taos = 1, all ones are transmitted at the tclk frequency lloop local loopback when lloop = 1, data input at tpos, tneg (tdata) is internally looped back and output on rpos, rneg (rdata). tclk is routed to rclk, through the jitter attenuator, if activated. rloop remote loopback when rloop = 1, clock and data recovered by the receiver are sent back through the transmit path and retransmitted. the clock and data are routed through the jitter attenuator, if activated. lbo[2:1] line build out lbo2 lbo1 attenuation 00 0 db 01 -7.5 db 1 0 -15 db 1 1 -22.5 db for e1 long haul, only the 0 db setting should be used when the part is configured for matched impedance drive. coder zero substitution (valid only when tneg (ubs) is tied high, invoking unipolar mode). in long haul mode, setting coder to 1 enables b8zs (hdb3) encoding and decoding. the substitution depends on whether the cs61581 is configured for t1 or e1 operation. via the e1_lh bit, cr3.6 (taz) transmit all zeroes (valid only when tneg (ubs) is tied low, invoking bipolar mode). when in bipolar mode (tpos/tneg are data inputs) setting taz to 1 causes all zeros to be transmitted. nloop network loopback nloop = 1 when a network loopback code has been detected on the received signal. an interrupt will occur when nloop changes state unless a 1 is written to nloop disabling the interrupt. los loss of signal los = 1 when the loss of signal criteria have been met (175 zeros). los = 0 when a valid signal is being received. an interrupt will occur when los changes state unless a 1 is written to los disabling the in- terrupt. 7 (msb)6543210 (lsb) taos lloop rloop lb02 lb01 coder taz nloop los cs61581 18 ds211f1
cs61581 ds211pp8 19 2.14 control register 1 sh (cr2.0 = 1): address 0x10 taos transmit all ones select when taos = 1, all ones are transmitted at the tclk frequency lloop local loopback when lloop = 1, data input at tpos/tneg (tdata) is internally looped back and output on rpos/rneg (rdata). tclk is routed to rclk, through the jitter attenuator, if activated. rloop remote loopback when rloop = 1, clock and data recovered by the receiver are sent back through the transmit path and retransmitted. the clock and data are routed through the jitter attenuator, if activated. len [2:0] line length selection allows selection of a variety of transmit pulse shapes. see table 1 for details. note that the selection of t1 or e1 pulse shapes determines the operation of the device. when matchz is set to 1 the transmitter s output impedance changes according to the pulse se- lected. for t1 pulses, the encoders and decoders are set to b8zs, and the qrss data pattern is 2 20 -1 with 14 consecutive zeros, max. for e1 pulses, the encoders and decoders are set to hdb3, and the qrss data pattern is 2 15 -1. rsvd this bit is reserved. los loss of signal los = 1 when the loss of signal criteria have been met (175 zeros). los = 0 when a valid signal is being received. an interrupt will occur when los changes state unless a 1 is written to los disabling the in- terrupt. 7 (msb)6543210 (lsb) taos lloop rloop len2 len1 len0 rsvd los cs61581 ds211f1 19
cs61581 20 ds211pp8 2.15 control register 2 lh: address 0x11 ais alarm indication signal. ais = 1 when an all ones pattern is present at the receiver. this bit is reset to 0 by the first read occurring after the ais condition has cleared. an interrupt will occur when ais is present unless a 1 is written to ais disabling the interrupt. ramplse when ramplse = 1, output pulse shapes are determined by the codes in the internal, pro- grammable, transmit ram. matchz matched impedance drive when matchz = 1 the output impedance is automatically set to match the impedance of a standard t1 or e1 line. a 1:1.5 transformer should be used when matchz = 1, and a 1:2 transformer should be used when matchz = 0. (see figures 15 and 16.) loopdn loop down in long haul mode, setting loopdn to 1 causes the data pattern 001001... to be repetitively transmitted. loopup loop up in long haul mode, setting loopup to 1 causes the data pattern 0000100001... to be repetitively transmitted. rpwdn receiver power down when rpwdn = 1, the receiver circuitry is powered down, but the transmitter is still active. txhiz transmitter high impedance when txhiz = 1 the transmitter goes to a low-power, high-impedance state sh/lh short haul / long haul select when sh/lh = 0, the cs61581 is in the long haul mode. when sh/lh = 1, the cs61581 is in the short haul mode. note that it overwrites the e1_lh bit, if set. sh/lh controls the functions of the bits in control register 1 (address 0x10) and control reg- ister 2 (address 0x11). 7 (msb) 6 5 4 3 2 1 0 (lsb) ais ramplse matchz loopdn loopup rpwdn txhiz sh/lh cs61581 20 ds211f1
cs61581 ds211pp8 21 2.16 control register 2 sh: address 0x11 ais alarm indication signal. ais = 1 when an all ones pattern is present at the receiver. this bit is reset to 0 by the first read occurring after the ais condition has cleared. an interrupt will occur when ais is present unless a 1 is written to ais disabling the interrupt. ramplse when ramplse = 1, output pulse shapes are determined by the codes in the internal ram. matchz matched impedance drive when matchz = 1 the output impedance is automatically set to match the impedance of a standard t1 or e1 line. a 1:1.5 transformer should be used when matchz = 1, and a 1:2 transformer should be used when matchz = 0. (see figures 15 and 16.) rsvd reserved. set to 0 for normal operation. rcoder receive decoder enable in short haul mode, when tneg is held high, setting rcoder to 1 causes the received data to be b8zs/hdb3 decoded (depends on t1 or e1 pulse shape selection). when rcoder is set to 0 the decoders are set for ami only. this bit has precedence over the external pin. tcoder transmit encoder enable in short haul mode, when tneg is held high, when tcoder = 1 the transmitter b8zs/hdb3 encoders are enabled (depends on t1 or e1 pulse shape selection). when tcoder is set to 0 the decoders are set for ami only. this bit has precedence over the external pin. txhiz transmitter high impedance when txhiz = 1 the transmitter goes to a low-power, high-impedance state sh/lh short haul / long haul select when sh/lh = 0, the cs61581 is in the long haul mode. when sh/lh = 1, the cs61581 is in the short haul mode. sh/lh controls the functions of the bits of control register 1 (address 0x10), and control reg- ister 2 (address 0x11). 2.17 equalizer gain (eqgain): address 0x12 eq[4:0] the receive equalizer gain settings are broken down into 20 segments and provided at the five lsbs of this register, eq4 - eq0. 00001 corresponds to -2 db, 10100 corresponds to -40 db. the three msbs are don t cares. 2.18 ram address (ram): address 0x13 ram[7:0] the ram address pointer for the arbitrary waveform memory; a special write procedure must be followed to write the waveform ram. 7 (msb) 6 5 4 3 2 1 0 (lsb) ais ramplse matchz rsvd rcoder tcoder txhiz sh/lh 7 (msb)6543210 (lsb) x x x eq4 eq3 eq2 eq1 eq0 7 (msb)6543210 (lsb) ram.7 ram.6 ram.5 ram.4 ram.3 ram.2 ram.1 ram.0 cs61581 ds211f1 21
cs61581 22 ds211pp8 2.19 control register 3 (cr3): address 0x14 qrsspath when qrsspath = 0 the qrss pattern will be output from the recovered data pins, rpos, rneg (rdata), and may be received at the transmitter inputs, tpos, tneg (tdata). when qrsspath = 1 the qrss pattern will be output from the line transmitter and may be received at the receiver. e1_lh e1 long haul when e1_lh = 1 and sh/lh (cr2.0) = 0, the following functionality applies: coder mode se- lects hdb3 coding and decoding; when matchz = 1, the output impedance of the transmitter will be set to match impedances near 120 . ; the qrss pattern is 2 15 -1; the jitter attenuator is adjusted for tbr12/13 compliance, with the knee in the frequency response at 1.25 hz. when e1_lh = 0 and sh/lh = 0, the following functionality applies: coder mode selects b8zs coding and decoding; when matchz = 1, the output impedance of the transmitter will be set to match impedances near 100 . ; the qrss pattern is 2 20 -1; the jitter attenuator is adjusted for at&t 62411 compliance, with the knee in the frequency response at 4 hz. this bit is ignored if sh/lh = 1. rst_qerr reset data pattern error count register setting rst_qerr to 1 will clear the qrss error count in the dpec register. this bit is automatically cleared and will read as 0. qdet qrss detector enable when qdet = 1, the qrss pattern detector is enabled. errors detected and counted are stored in the dpec register (address 0x15). ins_qerr qrss error insert setting ins_qerr to 1 and then 0 causes an error to be inserted in the output qrss pat- tern. qsync/test qsync reads as 1 to indicate when the qrss detector is synchronized to an input pattern. qsync is only valid when qdet = 1 enabling the pattern detector. when writing this register, this bit must be set to 0 for normal operation. qgen qrss generator enable when qgen = 1, the qrss generator is enabled. the qrss pattern is output at the ttip/tring pins, or at the rpos/rneg (rdata) pins, depending upon the state of the qrsspath bit. errors can be generated using the ins_qerr bit. test bit should be set to 0 for normal operation. 2.20 data pattern error count (dpec): address 0x15 dpec[7:0] errors detected in the input qrss pattern are counted and stored. this register saturates at 255 errors. the dpec is cleared when the rst_qerr bit is written in the cr3 register. 7 (msb) 6 5 4 3 2 1 0 (lsb) qrsspath e1_lh rst_qerr qdet ins_qerr qsync/test qgen test 7 (msb)6543210 (lsb) dpec.7 dpec.6 dpec.5 dpec.4 dpec.3 dpec.2 dpec.1 dpec.0 cs61581 22 ds211f1
cs61581 ds211pp8 23 2.21 interrupts an interrupt will occur (int pulls low) in response to a change in the los, ais or nloop bits. the interrupt is cleared when the host processor writes a ? 1 ? to the respective bit in the control register. writing a ? 1 ? to los or nloop over the serial in- terface has three effects: 1) the current interrupt on the serial interface will be cleared. (note that simply reading the regis- ter bits will not clear the interrupt). 2) output data bits 5, 6 and 7 will be reset as ap- propriate. 3) interrupts for the corresponding los and nloop will be prevented from occurring. writing a ? 0 ? to either los or nloop enables the corresponding interrupt for los and nloop. reading the registers returns their current status or setting. register 0x10 outputs the status nloop and los and has bits 5, 6, and 7 encoded as shown in tables 4 and 5. 3. qrss test mode in host mode, the cs61581 has the capability to generate and detect a qrss (2 20 -1 with 14 zeros _path bit (cr3.7) determines whether the pattern is transmitted on ttip/tring or rpos/rneg. errors can be inserted and counted in the pattern. the qrss test mode is controlled through control register 3, address 0x14. setting qgen to 1 (cr3.1 = 1) initiates the pattern output. the qrss pattern detector is enabled by writing a 1 to qdet (cr3.4 = 1). when the detector synchronizes to an input pattern, qsync is set to 1. errors detected in the received qrss pattern are counted and stored in the data pattern error count, dpec, register at address 0x15. an error can be inserted in the output data pattern by setting ins_qerr bit to 1 then 0. the number of errors accumulated by the pattern detec- tor are stored in the dpec register. the dpec reg- ister will accumulate to all ones, 255 errors, and stay at that level until reset. the dpec register is reset to zero by setting the rst_qerr bit to 1 (cr3.3 = 1) table 4. register 0x10 decoding bits long haul mode status 765 0 0 0 reset has occurred, or no program input 001rloop active 0 1 0 lloop active 0 1 1 los has changed state since last clear los occurred 100taos active 1 0 1 nloop has changed state since last clear nloop occurred 1 1 0 taos and lloop active 1 1 1 los and nloop have both changed state since last clear nloop and clear los table 5. register 0x10 decoding bits short haul mode status 765 0 0 0 reset has occurred, or no program input 001rloop active 010lloop active 0 1 1 los has changed state since last clear los occurred 100taos active 1 0 1 not used 1 1 0 taos and lloop active 1 1 1 not used cs61581 ds211f1 23
cs61581 24 ds211pp8 4. arbitrary waveform generation in addition to the predefined pulse shapes, the user can create custom pulse shapes using the host mode. this flexibility allows the board designer to accommodate non-standard cables, emi filters, protection circuitry, etc. the arbitrary pulse shape of mark (a transmitted 1) is specified by describing it ? s pulse shape across three unit intervals (uis). this allows, for exam- ple, the long-haul return-to-zero tail to extend into the next ui, or two uis, as is required for isolated pulses. each ui is divided into multiple phases, and the us- ers defines the amplitude of each phase. the wave- form of a space (a transmitted 0) is fixed at zero volts. examples of the phases are shown in figure 13. in all cases, to define an arbitrary wave- form, the user writes to the waveform register ei- ther 36, 39 or 42 times (12, 13 or 14 phases per ui for three uis). the phases are written in the order: ui1/phase1, ui1/phase2,..., ui1/phase14, ui2/phase1,..., ui2/phase14, ui3/phase1,..., ui3/phase14. for e1, short haul applications the cs61581 di- vides the 488 ns ui into 12 uniform phases (40.7 ns each), and will ignore the phase amplitude informa- tion written for phases 13 and 14 of each ui. for dsx-1 and ds1 applications, the cs61581 di- vides the 648 ns ui into 13 uniform phases (49.8 ns each), and will ignore the phase amplitude informa- tion written for phase 14 of each ui. for e1 long haul applications, the cs61581 divides the 648 ns ui into 14 uniform phases (46.3 ns each), and uses the phase information written for all 14 phases of each ui. when transmitting pulses, the cs61581 will add the amplitude information from the prior two sym- bols with the amplitude of the first ui of the current symbol before outputting a signal on ttip/tring. therefore, a mark preceded by two spaces will be output exactly as the mark is programmed. howev- er, when one mark is preceded by marks, the first portion of the last mark may be modified. with ami data, where successive pulses have opposite polarity, the undershoot tail of one pulse will cause the rising edge of the next mark to rise more quick- ly, as shown in figure 14. the amplitude of each phase is described by a 7-bit, two ? s compliment number, where a positive value describes pulse amplitude, and a negative value de- scribes pulse undershoot. the positive full value is 0x3f. the negative full value is 0x40. for t1, the typical output voltage is 38 mv/lsb. for e1 coax, the typical output voltage is 22 mv/lsb. for e1 shielded twisted pair, the typical output voltage is e1 arbitrary waveform example dsx-1 (54% duty cycle) arbitrary waveform example ds-1 (50% duty cycle) arbitrary waveform example figure 13. phase definition of arbitrary waveforms cs61581 24 ds211f1
cs61581 ds211pp8 25 27 mv/lsb. all voltages are peak voltages across the ttip and tring outputs. on the secondary of a 1:2 step-up transformer, the mv/lsb is twice the values stated above. note that although the full scale digital input is 3f, it is rec- ommended that full scale output voltage on the transformer primary be limited to 2.4 v peak. at higher output voltages, the driver may not drive the requested output voltage. writing the arbitrary waveform ram requires a deviation from normal serial port access. register 0x13 is the ram address register for the arbitrary waveform. two consecutive address bytes are writ- ten; first the address/command byte is written to address 0x13, followed by the address in ram to be written. this dual address is then followed by the data byte for the waveform amplitude. there are 42 ram byte locations (numbered 0x00 to 0x29). each phase amplitude is written as an eight- bit byte, where the first phase of the symbol is writ- ten first. the amplitude bytes are written lsb first. reading the arbitrary waveform ram follows the same sequence as the write, except the third mem- ory access in the sequence is a read instead of a write. 4.1 power on reset / reset upon power-up, the ic is held in a static state until the supply crosses a threshold of approximately 3 volts. when this threshold is crossed, the device will delay for about 10 ms to allow the power sup- ply to reach operating voltage. after this delay, cal- ibration of the transmit and receive sections commences. because power up conditions can vary considerably, it is recommended that the device be reset after the power supply has stabilized to ensure a known initial operational condition. the internal frequency generators can be calibrated only if a reference clock is present. the reference clock for the transmitter is provided by tclk. the reference for the receiver is either the crystal oscil- lator or mclk. if both the oscillator and mclk are active, mclk will be used as the reference source. the initial calibration should take less than 20 ms after pulses are input to the receiver. in operation, the device is continuously calibrated, making the performance of the device independent of power supply or temperature variations. the continuous calibration function forgoes any re- quirement to reset the line interface when in opera- tion. however, a reset function is available which will reinitiate calibration and clear all registers and clear the network loopback function. in host mode, a reset is initiated by simultaneously writing rloop and lloop to the register. the re- set will set all registers to ? 0 ? and initiate a calibra- tion. a reset will also set los high in the short haul configuration. in hardware mode, the cs61581 is reset by simul- taneously setting rloop and lloop high for at least 200 ns. hardware reset will clear network loopback functionality figure 14. example of summing of waveforms cs61581 ds211f1 25
cs61581 26 ds211pp8 4.2 power supply the device operates from a single +5 volt supply. separate pins for transmit and receive supplies pro- vide internal isolation. these pins should decou- pled to their respective grounds. tv+ must not exceed rv+ by more than 0.3 v. decoupling and filtering of the power supplies is crucial for the proper operation of the analog cir- cuits in both the transmit and receive paths. a 47 f tantalum and 1.0 f mylar or ceramic capacitor should be connected between tv+ and tgnd, and a 0.1 f mylar or ceramic capacitor should be con- nected between rv+ and rgnd. place capacitors as closely as possible to their respective power sup- ply pins. wire-wrap breadboarding of the line in- terface is not recommended because lead resistance and inductance serve to defeat the function of the decoupling capacitors. turns ratio: low impedance output/hardware mode 1:2 step-up transmit, 1:1 receive turns ratio: matched impedance output 1:1.5 step-up transmit, 1:1 receive primary inductance 1.2 mh min at 772 khz primary leakage inductance 0.5 h max at 772 khz with secondary shorted secondary leakage inductance 0.5 h max at 772 khz interwinding capacitance 40 pf max, primary to secondary et-constant 16 v- s min table 6. transformer specification diagnostic mode availability (note 25) h/w host host mode (note 26) maskable loopback modes local loopback (lloop) yes yes no remote loopback (rloop) yes yes no in-band network loopback (nloop) yes yes yes internal data pattern generation and detection transmit all ones (taos) yes yes no quasi-random signal source (qrss) no yes no in-band loop-up/down code generator no yes no error insertion and detection quasi-random signal detection (qdet) no yes no quasi-random signal error insertion (ins_qerr) no yes no bipolar violation detection (bpv) yes yes no alarm condition monitoring receive loss of signal monitoring (los) yes yes yes receive alarm indication signal monitoring (ais) no yes yes other diagnostic reports receive line attenuation indicator (latn) yes yes no notes: 25. in hardware mode the diagnostic modes are selected by directly setting the pins on the device; in host mode, the appropriate register bits are written for diagnostic modes. 26. in host mode the interrupts can be masked by writing a 1 to the los bit; there is no masking in the hardware mode. table 5. diagnostic mode availability cs61581 26 ds211f1
cs61581 ds211pp8 27 turns ratio(s) manufacturer part number package type 1:1ct pulse engineering pe-64936 1.5 kv, through-hole, single valor pt5008 schott 67130840 valor st5085 1.5 kv, surface mount, single schott 31187 1:2ct pulse engineering pe-65351 1.5 kv, through-hole, single valor pt5004 schott 617130850 valor st5086 1.5 kv, surface mount, single schott 31188 1:1.5ct pulse engineering t-1054 1.5 kv, through-hole, single schott 31705 valor st5074 1.5 kv, surface mount, single schott 31706 1:1ct 1:2ct pulse engineering pe-68678 1.5 kv, surface mount, dual valor st5162 pulse engineering pe-68877 1.5 kv, surface mount, dual extended temp. pulse engineering t-1068 1.5 kv, surface mount, quad port valor st5173 pulse engineering t-1031 3 kv, surface mount, dual 1:1ct 1:1.5ct pulse engineering t-1022 1.5 kv, surface mount, dual valor st5221 pulse engineering t-1077 1.5 kv, surface mount, dual extended temp pulse engineering t-1081 3 kv, surface mount, dual table 7. recommended transformers for the cs61581 cs61581 ds211f1 27
cs61581 28 ds211pp8 5. applications control & monitor frame format encoder/ decoder cs61581 in host mode receive line transmit line 28 1 12 6 5 7 6 8 3 4 2 9 10 rv+ + 33 f rgnd 0.1 f +5v 21 15 + 1.0 f tgnd rv+ tv+ clke mclk los bpv mode rpos rneg rclk tpos tneg tclk xtalin xtalout rgnd tgnd 22 14 sclk cs int sdi sdo rtip rring tring ttip 19 20 16 13 r1 r2 1 5 2 6 0.47 f 2 6 1 5 1:1.5 t-1054 1ct:1 pe-64936 p serial port 27 26 23 24 25 18 latn 1 k . 11 jasel 0.47 f figure 15. matched impedance output configuration t1 100 . e1 75 . e1 120 . r1 ( . ) 50 37.5 60 r2 ( . ) 50 37.5 60 cs61581 28 ds211f1
cs61581 ds211pp8 29 control & monitor frame format encoder/ decoder cs61581 in hardware mode line length setting 28 1 26 27 5 7 6 8 3 4 2 9 10 + 33 f rgnd 0.1 f +5v 21 15 + 1.0 f tgnd rv+ tv+ taos mclk rloop lloop mode rpos rneg rclk tpos tneg tclk xtalin xtalout rgnd tgnd 22 14 lbo2 lbo1 rtip rring tring ttip 24 25 1:2 pe-65351 12 23 los nloop 11 jasel receive line transmit line 19 20 16 13 r1 r2 1 5 2 6 0.47 f 2 6 1 5 1ct:1 pe-64936 0.47 f r3 r4 figure 16. low impedance output configuration t1 100 . e1 75 . e1 120 . r1 ( . ) 50 37.5 60 r2 ( . ) 50 37.5 60 r3 ( . ) 9.1 9.1 9.1 r4 ( . ) 9.1 9.1 9.1 cs61581 ds211f1 29
cs61581 30 ds211pp8 transmit line receive line tv+ rv+ mode rclk rpos rneg tclk tpos tneg sclk sdi sdo int cs +5v rmsync rfsync rsigsel rchclk rser rabcd tmo tsigsel tsigfr tchclk tser tabcd rlclk rlink tlclk tlink tmsync test vss rsigfr cs61581 tfsync vdd sps rclk rpos rneg tclk tpos tneg sclk sdi sdo int cs ryel rcl rbv rfer rlos rst data link supervision host processor 39 3 12 13 14 15 16 17 18 19 21 24 33 34 35 36 37 38 40 1 2 4 5 6 7 8 9 10 11 20 22 23 25 26 27 28 29 30 31 32 ttip tring rtip rring clke 1.544 mhz serial backplane control pcm data signalling pcm data signalling q q c d p q q c d p rmsync rsigsel slc-96 multiframe sync vdd (optional) backplane interface ? cs62180b figure 17. typical system connection cs61581 30 ds211f1
c s 6 1 5 8 1 d s 2 1 1 p p 8 3 1 6. pi n de s c r i pt i o n t o p v i e w 2 2 2 0 2 4 1 9 2 1 2 3 2 5 3 2 7 2 4 2 6 2 8 1 1 2 1 4 1 6 1 8 1 3 1 5 1 7 8 6 1 0 5 7 9 1 1 m c l k t c l k t a o s / c l k e t p o s / t d a t a l l o o p / s c l k t n e g / u b s r l o o p / c s m o d e l b o 2 / s d o r n e g / b p v l b o 1 / s d i r p o s / r d a t a n l o o p / i n t r c l k r g n d x t a l i n r v + x t a l o u t r r i n g j a s e l r t i p l o s l a t n t t i p n c t g n d t r i n g t v + cs61581 ds211f1 31
cs61581 32 ds211pp8 6.1 power supplies tv+ - power supply, transmit driver, pin 15. power supply for the transmit driver; typically +5 volts. tgnd - ground transmit driver, pin 14. power supply ground for the transmit driver; typically 0 volts. rv+ - power supply, pin 21. power supply for all subcircuits except the transmit driver; typically +5 volts. rgnd - ground, pin 22. power supply ground for all subcircuits except the transmit driver; typically 0 volts. 6.2 oscillator xtalin, xtalout - crystal connections, pins 9 and 10. a 6.176 mhz (or 8.192 mhz) crystal can be connected across these pins. this oscillator provides the reference frequency for the liu if mclk is not provided. the load capacitance presented to the crystal by these pins should be approximately 19 pf (ic and package, when soldered into a circuit board). the jitter attenuator may be disabled by tying xtalin to rv+ through a 1 k . resistor, and floating xtalout. when xtalin has no clock input, a clock must be supplied to the mclk pin. alternatively an external 6.176 mhz (8.192 mhz) clock can be driven into xtalin, and the jitter attenuator circuit will operate. if mclk is provided, and xtalin is tied low or floated, the jitter attenuator will be enabled. 6.3 control mclk - master clock input, pin 1. either mclk or the crystal oscillator provide the master frequency reference for the cs61581. if both mclk and the crystal oscillator are present, the oscillator is ignored. mclk should be 1.544 mhz for t1 and 2.048 mhz) for e1. in a loss of signal state, rclk will be derived from mclk, through the jitter attenuator, if active. if mclk is not provided, the jitter attenuator will hold the rclk frequency in a loss of signal state. mclk should be grounded if it is not used. mode - mode select input, pin 5. setting the mode pin high puts the cs61581 into host mode where the device is controlled by a microprocessor, via a serial port. setting the mode pin low, configures the part for hardware mode control where various control and status are provided on dedicated pins. the mode pin is internally pulled down placing the part in hardware mode when this pin is left floating. tying the mode pin to rclk places the chip in hardware mode and enables the b8zs encoder/decoder (provided that unipolar mode has been enabled; see the description for tneg/ubs pin). taos - transmit all ones select input, pin 28 (hardware mode). setting taos to logic 1 causes continuous ones to be transmitted at the tclk frequency. when taos is high, tpos and tneg (tdata) are not output at the ttip/tring pins. taos is overridden by remote loopback. setting taos, lloop, and rloop high simultaneously enables network loopback detection. cs61581 32 ds211f1
cs61581 ds211pp8 33 lloop - local loopback input, pin 27 (hardware mode). setting lloop to a logic 1 internally routes the transmitter input to the receiver output. if taos is low, the signal being output from the transmitter will be internally routed to the receiver inputs allowing nearly the entire chip to be tested. if taos and lloop are set high at the same time, the local loopback will occur at the jitter attenuator (excluding the transmit and receive circuitry) and the transmitter will transmit all ones. simultaneously setting rloop and lloop high while taos is low resets the cs61581. simultaneously setting rloop, lloop and taos high enables network loopback detection. rloop - remote loopback input, pin 26 (hardware mode). setting rloop to a logic 1 causes the received signal to be passed through the jitter attenuator (if active) and retransmitted onto the line. the internal encoders/decoders will be bypassed in remote loopback. simultaneously setting rloop and lloop high while taos is low resets the cs61581. simultaneously setting rloop, lloop and taos high enables network loopback detection. lbo1, lbo2 - line build out 1 and 2, pins 24 and 25 (hardware mode). transmitted line build out pulse shapes are selected by setting lbo[2:1] = 00 (0 db), 01 (-7.5 db), 10 (- 15 db), or 11 (-22.5 db). jasel - jitter attenuator select, pin 11. if the jitter attenuator is enabled (crystal oscillator active, or xtalin tied low or floated with mclk provided), setting jasel high places the jitter attenuator in the receive path; setting jasel low places the jitter attenuator in the transmit path. nc - no connect, pin 17. the input voltage to this pin does not effect normal operation. 6.4 status los - loss of signal output, pin 12. los goes high when 175 consecutive zeros are received. los returns low when the ones density reaches 12.5% (based on 175 consecutive bit periods, starting with a one and containing less than 100 consecutive zeros, as prescribed in ansi t1.231-1993 and itu-t g.775). if los is true, and the jitter attenuator is in the receive path, rclk will smoothly transition to mclk if provided; rclk will retain the frequency prior to los if mclk is grounded. if the jitter attenuator is not in the receive path, rclk will become the reference clock frequency (mclk) if provided, or the crystal oscillator. nloop - network loopback output, pin 23 (hardware mode). nloop goes high when a 00001 pattern is received for five seconds putting the cs61581 into network (remote) loopback. nloop is deactivated upon receipt of a 001 pattern for five seconds, or by selection of lloop or rloop. latn - line attenuation indication output, pin 18. latn is an encoded output that indicates the receive equalizer gain setting in relation to a five rclk cycle period. if latn is high for one rclk cycle, the equalizer is set for 7.5 db gain, two cycles = 15 db gain, three cycles = 22.5 db gain, four cycles = 0 db. latn may be sampled on the rising edge of rclk. 6.5 serial control interface int - interrupt output, pin 23 (host mode). int pulls low to flag the host processor when nloop, ais or los changes state. int is an open drain output and should be tied to the supply through a resistor. cs61581 ds211f1 33
cs61581 34 ds211pp8 sdi - serial data input, pin 24 (host mode). data input to the on-chip register is sampled on the rising edge of sclk. sdo - serial data output, pin 25 (host mode). status and control information are output from the on-chip register on sdo. if clke is high, sdo is valid on the rising edge of sclk. if clke is low, sdo is valid on the falling edge of sclk. sdo goes to a high-impedance state when the serial port is being written to, or after bit d7 is output or cs goes high (whichever occurs first). cs - chip select, pin 26 (host mode). the serial interface is accessible when cs transitions from high to low. sclk - serial clock input, pin 27 (host mode). sclk is used to write or read data bits to or from the serial port registers. clke - clock edge, pin 28 (host mode). setting clke to logic 1 causes rpos and rneg (rdata) to be valid on the falling edge of rclk, and sdo to be valid on the rising edge of sclk. conversely, setting clke to logic 0 causes rpos and rneg (rdata) to be valid on the rising edge of rclk and sdo to be valid on the falling edge of sclk. 6.6 data input/output tclk - transmit clock input, pin 2. the 1.544 mhz (2.048 mhz) transmit clock is input on this pin. tpos and tneg or tdata are sampled on the falling edge of tclk. tpos/tneg - transmit positive pulse, transmit negative pulse, pins 3 and 4. data input to tpos and tneg is sampled on the falling edge of tclk and transmitted onto the line at ttip and tring. an input on tpos results in transmission of a positive pulse; an input on tneg results in transmission of a negative pulse. if tneg is held high for 16 tclk cycles, the cs61581 reconfigures for unipolar (single pin nrz) data at pins 3 and 7, tdata and rdata. if tneg goes low the cs61581 switches back to two-pin bipolar data input format. the device should be reset when changing between unipolar and bipolar mode. tdata - transmit data, pin 3. when pin 4, tneg/ubs, is held high, pin 3 becomes tdata, a single-line nrz (unipolar) data input sampled on the falling edge of tclk. ubs - unipolar / bipolar select, pin 4. when ubs is held high for 16 consecutive tclk cycles (15 consecutive bipolar violations) the cs61581 reconfigures for unipolar (single-line nrz) data input / output format. pin 3 becomes tdata, pin 7 becomes rdata, and pin 6 becomes bpv. rclk - recovered clock output, pin 8. rclk outputs the clock recovered from the input signal at rtip and rring. in a loss of signal state rclk reverts to the mclk frequency, or retains the frequency prior to the los state, depending on the clocks provided. see the los pin description. rneg/rpos - receive negative pulse, receive positive pulse, pins 6 and 7. recovered data output on rpos and rneg is stable and valid on the rising edge of rclk in hardware mode. in host mode, clke determines the edge of rclk on which rpos and rneg are valid. a positive pulse on rtip with respect to rring generates a logic 1 on rpos; a positive pulse on rring with respect to rtip generates a logic 1 on rneg. cs61581 34 ds211f1
cs61581 ds211pp8 35 rdata - received data, pin 7. unipolar data (single-line nrz) data is output on rdata when tneg/ubs (pin 4), is held high. in host mode, clke determines the edge of rclk on which rdata is valid. bpv - bipolar violation, pin 6. when pin 4 is held high, received bipolar violations are flagged by bpv (rneg) going high along with the offending bit output from rdata. if the b8zs or hdb3 encoder/decoder is activated, bpv will not flag bipolar violations resulting from valid zero substitutions. ttip, tring - transmit tip and ring, pins 13, 16. the transmit signal to the line is sent out on these pins. they represent the signal driven on tclk, tpos, and tneg (or tdata). rtip, rring - receive tip and ring, pins 19, 20. the input pins for the receive signal from the line. they recovered clock and data driven on rclk, rpos, and rneg (or rdata). cs61581 ds211f1 35
cs61581 ds211pp8 37 inches millimeters dim min nom max min nom max a 0.165 0.1725 0.180 4.191 4.3815 4.572 a1 0.090 0.105 0.120 2.286 2.667 3.048 b 0.013 0.017 0.021 0.3302 0.4318 0.533 d 0.485 0.490 0.495 12.319 12.446 12.573 d1 0.450 0.453 0.456 11.430 11.506 11.582 d2 0.390 0.410 0.430 9.906 10.414 10.922 e 0.485 0.490 0.495 12.319 12.446 12.573 e1 0.450 0.453 0.456 11.430 11.506 11.582 e2 0.390 0.410 0.430 9.906 10.414 10.922 e 0.040 0.050 0.060 1.016 1.270 1.524 jedec # : ms-047 28l plcc package drawing d1 d e1 e d2/e2 b e a1 a cs61581 36 ds211f1
cs61581 ds211f1 37 revision date changes pp8 april ?00 preliminary release. f1 aug ?05 removed 28-pin pdip package option. contacting cirrus logic support for all product questions and inquiries contact a cirrus logic sales representative. to find the one nearest to you go to www.cirrus.com important notice cirrus logic, inc. and its subsidiaries (?cirrus?) believe that the information contained in this document is accurate and reli able. however, the information is subject t o change without notice and is provided ?as is? without warranty of any kind (express or implied). customers are advised to obtai n the latest version of relevant info r mation to verify, before placing orders, that information being relied on is current and complete. all products are sold subjec t to the terms and conditions of sale supplie d at the time of order acknowledgment, including those pertaining to warranty, indemnification, and limitation of liability. no r esponsibility is assumed by cirrus for th e use of this information, including use of this information as the basis for manufacture or sale of any items, or for infringeme nt of patents or other rights of third partie s this document is the property of cirrus and by furnishing this information, cirrus grants no license, express or implied under any patents, mask work rights, copyright s trademarks, trade secrets or other intellectual property rights. cirrus owns the copyrights associated with the information con tained herein and gives consent for copie s to be made of the information only for use within your organization with respect to cirrus integrated circuits or other product s of cirrus. this consent does not exten d to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for re sale. certain applications us ing semiconductor products may invo lve potential risks of death, personal injury, or severe prope r ty or environmental damage (? critical applications?). cirrus products are not designed, auth orized or warranted for use i n aircraft systems, military applications, products surgically implanted into the body, automotive safety or security device s life support products or other cr itical applications. inclusio n of cirrus products in such appl ications is u nderstood to b e fully at the customer's risk and cirrus disclaims and makes no warranty, express, statutory or implied, including the implie d warranties of merchantability and fitness for particular purpose, with regard to any cirrus product that is used in such a manner. if the customer or cu stomer's customer us es or permits the use of cirrus prod ucts in critical app lications, custo m er agrees, by such use, to fully indemnif y cirrus, its officers, directors, employees, distributors and other agents from an y and all liability, including attorneys' fees and costs, that may result from or arise in connection with these uses. cirrus logic, cirrus, and the cirrus logic logo designs are tradem arks of cirrus logic, inc. all other brand and product names in this document may be trademarks o service marks of their respective owners.

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